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TPS54622 Datasheet(PDF) 24 Page - Texas Instruments

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Part No. TPS54622
Description  4.5-V to 17-V Input, 6-A Synchronous Step-Down SWIFT Converter With Hiccup Protection
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Manufacturer  TI1 [Texas Instruments]
Direct Link  http://www.ti.com
Logo TI1 - Texas Instruments

TPS54622 Datasheet(HTML) 24 Page - Texas Instruments

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TPS54622
SLVSA70E – MARCH 2011 – REVISED DECEMBER 2016
www.ti.com
Product Folder Links: TPS54622
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Copyright © 2011–2016, Texas Instruments Incorporated
8.2.2 Detailed Design Procedures
8.2.2.1 Operating Frequency
The first step is to decide on a switching frequency for the regulator. There is a trade off between higher and
lower switching frequencies. Higher switching frequencies may produce smaller a solution size using lower
valued inductors and smaller output capacitors compared to a power supply that switches at a lower frequency.
However, the higher switching frequency causes extra switching losses, which hurt the converter’s efficiency and
thermal performance. In this design, a moderate switching frequency of 480 kHz is selected to achieve both a
small solution size and a high-efficiency operation.
8.2.2.2 Output Inductor Selection
To calculate the value of the output inductor, use Equation 18. KIND is a coefficient that represents the amount
of inductor ripple current relative to the maximum output current. The inductor ripple current is filtered by the
output capacitor. Therefore, choosing high inductor ripple currents impact the selection of the output capacitor
since the output capacitor must have a ripple current rating equal to or greater than the inductor ripple current. In
general, the inductor ripple value is at the discretion of the designer; however, KIND is normally from 0.1 to 0.3
for the majority of applications.
(18)
For this design example, use KIND = 0.3 and the inductor value is calculated to be 3.08 µH. For this design, a
nearest standard value was chosen: 3.3 µH. For the output filter inductor, it is important that the RMS current
and saturation current ratings not be exceeded. The RMS and peak inductor current can be found from
Equation 20 and Equation 21.
(19)
(20)
(21)
For this design, the RMS inductor current is 6.02 A and the peak inductor current is 6.84 A. The chosen inductor
is a Coilcraft MSS1048 series 3.3 µH. It has a saturation current rating of 7.38 A and a RMS current rating of
7.22 A.
The current flowing through the inductor is the inductor ripple current plus the output current. During power-up,
faults or transient load conditions, the inductor current can increase above the calculated peak inductor current
level calculated above. In transient conditions, the inductor current can increase up to the switch current limit of
the device. For this reason, the most conservative approach is to specify an inductor with a saturation current
rating equal to or greater than the switch current limit rather than the peak inductor current.
8.2.2.3 Output Capacitor Selection
There are three primary considerations for selecting the value of the output capacitor. The output capacitor
determines the modulator pole, the output voltage ripple, and how the regulator responds to a large change in
load current. The output capacitance needs to be selected based on the more stringent of these three criteria.
The desired response to a large change in the load current is the first criteria. The output capacitor needs to
supply the load with current when the regulator can not. This situation would occur if there are desired hold-up
times for the regulator where the output capacitor must hold the output voltage above a certain level for a
specified amount of time after the input power is removed. The regulator is also temporarily not able to supply
sufficient output current if there is a large, fast increase in the current needs of the load such as a transition from
no load to full load. The regulator usually needs two or more clock cycles for the control loop to see the change


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