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ISL6219ACA-T Datasheet(PDF) 14 Page - Intersil Corporation |
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ISL6219ACA-T Datasheet(HTML) 14 Page - Intersil Corporation |
14 / 17 page 14 defined below, there is a separate set of equations for the compensation components. In Equations 17, L is the per-channel filter inductance divided by the number of active channels; C is the sum total of all output capacitors; ESR is the equivalent-series resistance of the bulk output-filter capacitance; and VPP is the peak-to-peak sawtooth signal amplitude as described in Figure 5 and Electrical Specifications. Once selected, the compensation values in Equations 17 assure a stable converter with reasonable transient perfor- mance. In most cases, transient performance can be improved by making adjustments to RC. Slowly increase the value of RC while observing the transient performance on an oscilloscope until no further improvement is noted. Normally, CC will not need adjustment. Keep the value of CC from Equations 17 unless some performance issue is noted. The optional capacitor C2, is sometimes needed to bypass noise away from the PWM comparator (see Figure 5). Keep a position available for C2, and be prepared to install a high- frequency capacitor of between 22pF and 150pF in case any jitter problem is noted. COMPENSATION WITHOUT LOAD-LINE REGULATION The non load-line regulated converter is accurately modeled as a voltage-mode regulator with two poles at the L-C resonant frequency and a zero at the ESR frequency. A type III controller, as shown in Figure 12, provides the necessary compensation. The first step is to choose the desired bandwidth, f0, of the compensated system. Choose a frequency high enough to assure adequate transient performance but not higher than 1/3 of the switching frequency. The type-III compensator has an extra high-frequency pole, fHF. This pole can be used for added noise rejection or to assure adequate attenuation at the error-amplifier high-order pole and zero frequencies. A good general rule is to chose fHF =10 f0, but it can be higher if desired. Choosing fHF to be lower than 10 f0 can cause problems with too much phase shift below the system bandwidth. In the solutions to the compensation equations, there is a single degree of freedom. For the solutions presented in Equations 18, RFB is selected arbitrarily. The remaining compensation components are then selected according to Equations 18. 1 2 π LC ------------------- f 0 > R C R FB 2 πf 0 Vpp LC 0.75V IN ------------------------------------ = C C 0.75V IN 2 πV PPRFBf0 ------------------------------------ = Case 1: 1 2 π LC ------------------- f 0 1 2 πC ESR () ------------------------------ < ≤ R C R FB V PP 2π ()2 f 0 2 LC 0.75 V IN -------------------------------------------- = C C 0.75 V IN 2 π ()2 f 0 2 V PPRFB LC ------------------------------------------------------------- = Case 2: (EQ. 17) f 0 1 2 πC ESR () ------------------------------ > R C R FB 2 π f 0VppL 0.75 V IN ESR () ------------------------------------------ = C C 0.75V IN ES R () C 2 πV PPRFBf0 L ------------------------------------------------- = Case 3: FIGURE 12. COMPENSATION CIRCUIT FOR ISL6219A BASED CONVERTER WITHOUT LOAD-LINE REGULATION. COMP CC RC RFB FB VSEN - + VDROOP C2 C1 R1 R 1 R FB CESR () LC C ESR () – ----------------------------------------- = C 1 LC C ESR () – R FB ----------------------------------------- = C 2 0.75 V IN 2 π ()2f 0fHF LCRFBVPP ------------------------------------------------------------------- = (EQ. 18) R C V PP 2π 2f 0 fHF LC 0.75 V IN 2 π f HF LC 1 – ---------------------------------------------------------------------- = C C 0.75V IN 2 πV PPRFB f 0 1 1 2 πf HF LC ----------------------------- – ---------------------------------------------------------------------------------- = ISL6219A |
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