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OPA686 Datasheet(PDF) 11 Page - Burr-Brown (TI) |
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OPA686 Datasheet(HTML) 11 Page - Burr-Brown (TI) |
11 / 15 page 11 ® OPA686 the primary through to the secondary as a 200 Ω source impedance and likewise, the 200 Ω R G resistor is reflected through to the transformer primary as a 50 Ω input match- ing impedance. The noise gain (NG) to the amplifier output is then 1+ 1000/400 = 3.5V/V. Taking the op amp’s 1.3nV/ √Hz input voltage noise times this noise gain to the output, then reflecting this noise term to the input side of the RG resistor, divides it by 5. This gives a net gain of 0.7 for the non-inverting input voltage noise when reflected to the input point for the op amp circuit. This is further reduced when referred back to the transformer primary. The 14dB gain to the matched load for the circuit of Figure 6 is precisely controlled ( ±0.2dB) and gives a 6dB noise figure at the input of the transformer. The DC noise gain for this circuit (3.5) is below the specified minimum stable gain. This will improve the distortion performance at frequencies below 20MHz from those shown in the Typical Performance Curves. Adding the inverting compensation capacitors holds this configuration stable as described in the previous section. Measured results show 140MHz small-signal bandwidth for the circuit of Figure 6 with ±0.1dB flatness through 50MHz. The OPA686 will easily deliver a 2Vp-p ADC full-scale input at the matched 50 Ω load. Two-tone testing at 20MHz for the circuit of Figure 6 (1Vp-p for each test tone) shows that the two-tone intermodulation intercept has improved to 40dBm versus the 35dBm shown in the Typical Perfor- mance Curves, giving a 72dBc SFDR for the two 4dBm test tones at the load . DESIGN-IN TOOLS DEMONSTRATION BOARDS Two PC boards are available to assist in the initial evaluation of circuit performance using the OPA686 in its two package styles. Both of these are available free as an unpopulated PC board delivered with descriptive documentation. The sum- mary information for these boards is shown in the table below. BOARD LITERATURE PART REQUEST PRODUCT PACKAGE NUMBER NUMBER OPA686U 8-Pin SO-8 DEM-OPA68xU MKT-351 OPA686N 5-Lead SOT23-5 DEM-OPA6xxN MKT-348 Contact the Burr-Brown applications support line to request any of these boards. MACROMODELS AND APPLICATIONS SUPPORT Computer simulation of circuit performance using SPICE is often useful when analyzing the performance of analog circuits and systems. This is particularly true for video and RF amplifier circuits where parasitic capacitance and induc- tance can have a major effect on circuit performance. A SPICE model for the OPA686 is available through either the Burr-Brown Internet web page (http://www.burr-brown.com) or as one model on a disk from the Burr-Brown Applications department (1-800-548-6132). The Applications department is also available for design assistance at this number. These models do a good job of predicting small-signal AC and transient performance under a wide variety of operating conditions. They do not do as well in predicting the har- monic distortion characteristics. These models do not at- tempt to distinguish between the package types in their small-signal AC performance. OPERATING SUGGESTIONS SETTING RESISTOR VALUES TO MINIMIZE NOISE The OPA686 provides a very low input noise voltage while requiring a low 12mA quiescent current. To take full advan- tage of this low input noise, careful attention to the other possible noise contributors is required. Figure 7 shows the op amp noise analysis model with all the noise terms included. In this model, all the noise terms are taken to be noise voltage or current density terms in either nV/ √Hz or pA/ √Hz. The total output spot noise voltage can be computed as the square root of the squared contributing terms to the output noise voltage. This computation adds all the contributing noise powers at the output by superposition, then takes the square root to get back to a spot noise voltage. Equation 1 shows the general form for this output noise voltage using the terms shown in Figure 7. Equation 1 Dividing this expression by the noise gain (NG = 1+RF/RG) will give the equivalent input-referred spot noise voltage at the non-inverting input as shown in Equation 2. Equation 2 4kT R G R G R F R S OPA686 I BI E O I BN 4kT = 1.6E –20J at 290°K E RS E NI 4kTR S √ 4kTR F √ E O = E NI 2 + I BN RS ()2 +4kTR S ()NG2 + I BI R F ()2 +4kTR F NG E N = E NI 2 + I BN RS ()2 +4kTR S + I BI R F NG 2 + 4 kTR F NG FIGURE 7. Op Amp Noise Analysis Model. |
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