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ISL6310 Datasheet(PDF) 9 Page - Intersil Corporation

Part No. ISL6310
Description  Two-Phase Buck PWM Controller with High Current Integrated MOSFET Drivers
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Maker  INTERSIL [Intersil Corporation]
Homepage  http://www.intersil.com/cda/home
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ISL6310 Datasheet(HTML) 9 Page - Intersil Corporation

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9
FN9209.3
December 12, 2006
external series gate resistors as this might lead to shoot-
through.
PGOOD (Pin 28)
PGOOD is used as an indication of the end of soft-start. It is
an open-drain logic output that is low impedance until the soft-
start is completed and Vout is equal to the VID setting. Once in
normal operation PGOOD indicates whether the output
voltage is within specified overvoltage and undervoltage limits.
If the output voltage exceeds these limits or a reset event
occurs (such as an overcurrent event), PGOOD becomes
high impedance again. The potential at this pin should not
exceed that of the potential at VCC pin by more than a typical
forward diode drop at any time
OVP (Pin 22)
Overvoltage protection pin. This pin pulls to VCC when an
overvoltage condition is detected. Connect this pin to the
gate of an SCR or MOSFET tied across VIN and ground to
prevent damage to a load device.
Operation
Multi-Phase Power Conversion
Modern low voltage DC/DC converter load current profiles
have changed to the point that the advantages of multi-
phase power conversion are impossible to ignore. The
technical challenges associated with producing a single-
phase converter that is both cost-effective and thermally
viable have forced a change to the cost-saving approach of
multi-phase. The ISL6310 controller helps simplify
implementation by integrating vital functions and requiring
minimal external components. The block diagram on page 2
provides a top level view of multi-phase power conversion
using the ISL6310 controller.
Interleaving
The switching of each channel in an ISL6310-based
converter is timed to be symmetrically out of phase with the
other channel. As a result, the two-phase converter has a
combined ripple frequency twice the frequency of one of its
phases. In addition, the peak-to-peak amplitude of the
combined inductor currents is proportionately reduced
(Equations 1 and 2).
Increased ripple frequency and lower ripple amplitude
generally translate to lower per-channel inductance and
lower total output capacitance for a given set of performance
specifications. Figure 1 illustrates the additive effect on
output ripple frequency. The two channel currents (IL1 and
IL2), combine to form the AC ripple current and the DC load
current. The ripple component has two times the ripple
frequency of each individual channel current.
To understand the reduction of ripple current amplitude in the
multi-phase circuit, examine the equation representing an
individual channel peak-to-peak inductor current.
In Equation 1, VIN and VOUT are the input and output
voltages respectively, L is the single-channel inductor value,
and FSW is the switching frequency.
The output capacitors conduct the ripple component of the
inductor current. In the case of multi-phase converters, the
capacitor current is the sum of the ripple currents from each
of the individual channels. Compare Equation 1 to the
expression for the peak-to-peak current after the summation
of N symmetrically phase-shifted inductor currents in
Equation 2. Peak-to-peak ripple current decreases by an
amount proportional to the number of channels. Output
voltage ripple is a function of capacitance, capacitor
equivalent series resistance (ESR), and inductor ripple
current. Reducing the inductor ripple current allows the
designer to use fewer or less costly output capacitors.
Another benefit of interleaving is to reduce input ripple
current. Input capacitance is determined in part by the
maximum input ripple current. Multi-phase topologies can
improve overall system cost and size by lowering input ripple
current and allowing the designer to reduce the cost of input
capacitance. The example in Figure 2 illustrates input
currents from a two-phase converter combining to reduce
the total input ripple current.
FIGURE 1. PWM AND INDUCTOR-CURRENT WAVEFORMS
FOR 2-PHASE CONVERTER
PWM2
PWM1
IL2
IL1
IL1 + IL2
I
PP
V
IN
V
OUT
() V
OUT
LF
SW
V
IN
⋅⋅
----------------------------------------------------------
=
(EQ. 1)
I
CPP
,
V
IN
NV
OUT
() V
OUT
LF
SW
V
IN
--------------------------------------------------------------------
=
(EQ. 2)
ISL6310


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