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HIP6601A Datasheet(PDF) 6 Page - Intersil Corporation |
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HIP6601A Datasheet(HTML) 6 Page - Intersil Corporation |
6 / 11 page 6 A falling transition on PWM indicates the turn-off of the upper MOSFET and the turn-on of the lower MOSFET. A short propagation delay [tPDLUGATE] is encountered before the upper gate begins to fall [tFUGATE]. Again, the adaptive shoot-through circuitry determines the lower gate delay time, tPDHLGATE. The PHASE voltage is monitored and the lower gate is allowed to rise after PHASE drops below 0.5V. The lower gate then rises [tRLGATE], turning on the lower MOSFET. Three-State PWM Input A unique feature of the HIP660X drivers is the addition of a shutdown window to the PWM input. If the PWM signal enters and remains within the shutdown window for a set holdoff time, the output drivers are disabled and both MOSFET gates are pulled and held low. The shutdown state is removed when the PWM signal moves outside the shutdown window. Otherwise, the PWM rising and falling thresholds outlined in the ELECTRICAL SPECIFICATIONS determine when the lower and upper gates are enabled. Adaptive Shoot-Through Protection Both drivers incorporate adaptive shoot-through protection to prevent upper and lower MOSFETs from conducting simultaneously and shorting the input supply. This is accomplished by ensuring the falling gate has turned off one MOSFET before the other is allowed to rise. During turn-off of the lower MOSFET, the LGATE voltage is monitored until it reaches a 2.2V threshold, at which time the UGATE is released to rise. Adaptive shoot-through circuitry monitors the PHASE voltage during UGATE turn-off. Once PHASE has dropped below a threshold of 0.5V, the LGATE is allowed to rise. PHASE continues to be monitored during the lower gate rise time. If PHASE has not dropped below 0.5V within 250ns, LGATE is taken high to keep the bootstrap capacitor charged. If the PHASE voltage exceeds the 0.5V threshold during this period and remains high for longer than 2 µs, the LGATE transitions low. Both upper and lower gates are then held low until the next rising edge of the PWM signal. Power-On Reset (POR) Function During initial startup, the VCC voltage rise is monitored and gate drives are held low until a typical VCC rising threshold of 9.95V is reached. Once the rising VCC threshold is exceeded, the PWM input signal takes control of the gate drives. If VCC drops below a typical VCC falling threshold of 9.2V during operation, then both gate drives are again held low. This condition persists until the VCC voltage exceeds the VCC rising threshold. Internal Bootstrap Device The HIP6601A, HIP6603A, and HIP6604 drivers all feature an internal bootstrap device. Simply adding an external capacitor across the BOOT and PHASE pins completes the bootstrap circuit. The bootstrap capacitor must have a maximum voltage rating above VCC + 5V. The bootstrap capacitor can be chosen from the following equation: Where QGATE is the amount of gate charge required to fully charge the gate of the upper MOSFET. The ∆V BOOT term is defined as the allowable droop in the rail of the upper drive. As an example, suppose a HUF76139 is chosen as the upper MOSFET. The gate charge, QGATE, from the data sheet is 65nC for a 10V upper gate drive. We will assume a 200mV droop in drive voltage over the PWM cycle. We find that a bootstrap capacitance of at least 0.325 µF is required. The next larger standard value capacitance is 0.33 µF. In applications which require down conversion from +12V or higher and PVCC is connected to a +12V source, a boot resistor in series with the boot capacitor is required. The increased power density of these designs tend to lead to increased ringing on the BOOT and PHASE nodes, due to faster switching of larger currents across given circuit parasitic elements. The addition of the boot resistor allows for tuning of the circuit until the peak ringing on BOOT is below 29V from BOOT to GND and 17V from BOOT to VCC. A boot resistor value of 5 Ω typically meets this criteria. In some applications, a well tuned boot resistor reduces the ringing on the BOOT pin, but the PHASE to GND peak ringing exceeds 17V. A gate resistor placed in the UGATE trace between the controller and upper MOSGET gate is recommended to reduce the ringing on the PHASE node by slowing down the upper MOSFET turn-on. A gate resistor value between 2 Ω to 10Ω typically reduces the PHASE to GND peak ringing below 17V. Gate Drive Voltage Versatility The HIP6601A and HIP6603A provide the user total flexibility in choosing the gate drive voltage. The HIP6601A lower gate drive is fixed to VCC [+12V], but the upper drive rail can range from 12V down to 5V depending on what voltage is applied to PVCC. The HIP6603A ties the upper and lower drive rails together. Simply applying a voltage from 5V up to 12V on PVCC will set both driver rail voltages. Power Dissipation Package power dissipation is mainly a function of the switching frequency and total gate charge of the selected MOSFETs. Calculating the power dissipation in the driver for a desired application is critical to ensuring safe operation. Exceeding the maximum allowable power dissipation level will push the IC beyond the maximum recommended operating junction temperature of 125oC. The maximum allowable IC power dissipation for the SO8 package is approximately 800mW. When designing the driver into an application, it is recommended that the following calculation C BOOT Q GATE ∆V BOOT ------------------------ ≥ HIP6601A, HIP6603A, HIP6604 |
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