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KH560 Datasheet(PDF) 10 Page - Fairchild Semiconductor

Part # KH560
Description  Wideband, Low Distortion Driver Amplifier
Download  13 Pages
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Manufacturer  FAIRCHILD [Fairchild Semiconductor]
Direct Link  http://www.fairchildsemi.com
Logo FAIRCHILD - Fairchild Semiconductor

KH560 Datasheet(HTML) 10 Page - Fairchild Semiconductor

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DATA SHEET
KH560
10
REV. 1A February 2001
the impact internal amplifier characteristics have on the
signal gain. Both the output DC error and noise model
may be developed using the equivalent model of Figure
5. Generally, non-inverting input errors show up at the
output with the same gain as the input signal, while the
inverting current errors have a gain of simply (Rf - Ro) to
the output voltage (neglecting the Ro to RL attenuation).
Output DC Offset:
The DC error terms shown in the specification listing
along with the model of Figure 5 may be used to estimate
the output DC offset voltage and drift. Each term shown
in the specification listing can be of either polarity. While
the equations shown below are for output offset voltage,
the same equation may be used for the drift with each
term replaced by its temperature drift value shown in the
specification listing.
Recall that the source impedance, Rs, includes both the
terminating and signal source impedance and that the
actual DC level to the load includes the voltage divider
between Ro and RL. Also note that for the KH560, as well
as for all current feedback amplifiers, the non-inverting
and inverting bias currents do not track each other in
either magnitude or polarity. Hence, there is no meaning
in an offset current specification, and source impedance
matching to cancel bias currents is ineffective.
Noise Analysis:
Although the DC error terms are in fact random, the cal-
culation shown above assumes they are all additive in a
worst case sense. The effect of all the various noise
sources are combined as a root sum of squared terms to
get an overall expression for the spot noise voltage. The
circuit of Figure 8 shows the equivalent circuit with all the
various noise voltages and currents included along with
their gains to the output.
where:
Gain to eo
eni – non-inverting input voltage noise
Av
ini – non-inverting input current noise
AvRs
ii – inverting input current noise
Rf - Ro
Av
Rf - Ro
1
1
Figure 8: Equivalent Noise Model
To get an expression for the equivalent output noise volt-
age, each of these noise voltage and current terms must
be taken to the output through their appropriate gains
and combined as the root sum of squares.
Where the 4kT(Rf - Ro) Av term is the combined noise
power of Rg and Rf - Ro.
It is often more useful to show the noise as an equivalent
input spot noise voltage where every term shown above
is reflected to the input. This allows a direct measure of
the input signal to noise ratio. This is done by dividing
every term inside the radical by the signal voltage gain
squared. This, and an example calculation for the circuit
of Figure 1, are shown below.
Note that RL may be
neglected in this calculation.
VI
R
V
1
RR
R
IR
R
where: I
non inverting bias current
I
inverting bias current
V
input offset voltage
V
5 A 25
2.0mV 10 10 A 360
12.4mV
attentuation between R and R
os
bn
s
io
f
o
g
bi
f
o
bn
bi
io
o
oL
1/ 2
=⋅
±
()⋅+ −
 ±−
()
≡−
=⋅
±
() ±
()
[]
µµ
ΩΩ L
An example calculation for the circuit in Figure 1 using
typical 25°C DC error terms and Rs = 25Ω, RL = 50Ω
yields:
Rg
ii
eo
Ro
Rf - Ro
Classical
op-amp
+
-
√4kTRVo
√4kT(Rf - Ro)
*
*
√4kTRs
4kT
Rg
*
*
Rs
ini
*
*
*
eni
4
4
4
4
kTR
source resis
ce voltage
noise
kT R
gain settling resistor
noise current
kT R
R
feedback resistor
voltage noise
kTR
output resistor voltage noise
s
g
f
o
o
()
tan
/
e
e
i R
kTR
A
i
R
R
kT R
R
A
kTR
oni
ni s
s
v
i
f
o
f
ov
o
=+
() +
() +−
()
+−
() +
2
2
22
2
4
44
L
e
e
i R
kTR
iR
R
A
kT R
R
A
kTR
A
nni
ni s
s
i
f
o
v
f
o
v
o
v
=+
() ++
()
+
()
+
2
2
2
2
2
2
4
4
4
L
DC


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