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AN-7510 Datasheet(PDF) 2 Page - Fairchild Semiconductor |
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AN-7510 Datasheet(HTML) 2 Page - Fairchild Semiconductor |
2 / 13 page ©2002 Fairchild Semiconductor Corporation Application Note 7510 Rev. A1 Driving constraints for this work were: 5. The SPICE device equations should not be modified. 6. Global temperature should be included. 7. All modes and levels of power MOSFET operation should be modeled. 8. The sub-circuit should be empirically developed to complement the device physics and the source code algorithms. 9. The sub-circuit should be acceptable to a circuit design user. 10. Parameter extraction should require little or no iteration. Temperature Modeling Use is made of voltage controlled voltage sources and model statements in order to form master/slave circuit relationships. In this manner, resistors can often be used to establish a first and second order temperature correction where direct PSpice algorithms will not permit thermal modeling. An Overview (Figure 1) The primary device for gate controlled positive or negative current flow is provided by Mos1 which is defined by the level 1 model MOSMOD. The second order effect of threshold voltage is set by Mos2 combined with the voltage VTO. Model MOSMOD also defines Mos2 but with a 1 percent scaling. It is necessary that RSOURCE and RDRAIN be provided as separate resistors, rather than being included with the MOS- FETs. In this manner, 1st and 2nd order temperature effects may be added as described by model RDSMOD. The thermal variation of KP as provided by the source code is a satisfactory representation. However, the threshold voltage of Mos1 must be modified by the voltage dependent voltage source EVTO. EVTO provides an additive or subtrac- tive voltage in series with the gate as a function of tempera- ture. It is equal to the sum of VBAT and the product of It and RVTO. Temperature variation is provided by model RVTO- MOD. Avalanche breakdown of the MOSFET is provided by the clamp circuit of DBREAK in series with EBREAK. The value of EBREAK is provided by the multiplier of EBREAK and the product of It times RBREAK. Temperature variation is pro- vided by model RBKMOD. High current voltage drops are provided by RS of the model DBKMOD including thermal sensitivity. The power MOSFET being modelled contains a third quad- rant diode as a fabrication consequence, and it is repre- sented by DBODY. Model DBDMOD provides the leakage current IS, the transit time for stored charge effects TT, the body diode series resistance RS, temperature dependence of this resistor TRS1 and TRS2, and the MOSFET output capacitance CJO. The inductances associated with the device terminals are represented by LSOURCE, LGATE, and LDRAIN. The effective series resistance associated with the gate is modelled by the resistor RGATE. A gate to source input capacitance is represented by CIN. MOSFET output capacitance is provided by model DBD- MOD as described above. Feedback capacitance is provided by DPLCAP as defined by model DPLCAPMOD. A diode was used for this function to provide a square root dependency with drain to source voltage. The voltage dependent voltage generator ESG is added to assure that the drain to source voltage is imposed across the feedback capacitor while forc- ing the feedback current flow into the gate node. It is further necessary that the ideality factor N of model DPLCAPMOD be made large to exclude forward diode conduction during third quadrant operation of the MOSFET. A capacitor CA is switched in parallel with CIN when the gate to source voltage becomes sufficiently negative. This switch- ing is implemented by the switch S1A. Model S1AMOD defines the switch closed resistance, open resistance, and the gate to source voltages through which the fully on to fully off transition occurs. During this transition, switch S1B also transitions from fully off to fully on. Switch S1B is defined by model S1BMOD. Voltage controlled voltage generator EGS provides the proper charge state for CA when switch S1A is open. In a similar manner, the capacitor CB is switched in parallel with CIN when the drain to gate voltage becomes negative. Switch S2A is defined by model S2AMOD for the on resis- tance, off resistance, and drain to gate voltage transition range. During this transition switch S2B also transitions as defined by model S2BMOD. Voltage controlled voltage gen- erators EDS and EGS provide the proper charge state for CB when switch S2A is open. In order to facilitate DC convergence, PSPICE provides a minimum conductance between all nodes as defined by the PSPICE analysis options. In order to assure that a floating gate initial condition will not exist should a modeler drive from a current source, a very large gate to source resistor RIN is added. Inclusion of RIN is recommended but not required. All sub-circuit elements are treated as being independent of temperature if they are not otherwise defined. Gate propagation effects [15], radiation effects, and inherent VDMOS design deficiencies are not modelled. This is discussed later. All discussions apply equally to P channel although N channel is discussed exclusively. Applications The sub-circuit combined with external circuitry may be analyzed for many responses. Three circuits are modelled to demonstrate the capability of the PSPICE sub-circuit model. A synchronous rectifier producing 100 watts at 5 volts DC from a 100KHz square wave demonstrates the ability to handle the first and third quadrant regimes of two MOSFETs, including conversion efficiency versus temperature. Calcu- lated waveforms are presented, but they are unsupported by measured data. The diode recovery waveform is modelled Application Note 7510 |
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