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AN-6754A Datasheet(PDF) 5 Page - Fairchild Semiconductor |
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AN-6754A Datasheet(HTML) 5 Page - Fairchild Semiconductor |
5 / 9 page AN-6754A APPLICATION NOTE © 2010 Fairchild Semiconductor Corporation www.fairchildsemi.com Rev. 1.0.0 • 10/8/10 5 Leading-Edge Blanking (LEB) Each time the power MOSFET is switched on, a turn-on spike occurs across the sense-resistor, RS in Figure 11, caused by primary-side capacitance and secondary-side rectifier reverse recovery. To avoid premature termination of the switching pulse, a leading-edge blanking time is built in. During this blanking period (280ns), the PWM comparator is disabled and cannot switch off the gate driver. Thus, RC filter with a small RC time constant (e.g. 100Ω + 470pF) is enough for current sensing. A non-inductive resistor for RS is recommended. Figure 11. Turn-On Spike Output Driver / Soft Driving The output stage is a fast totem-pole gate driver capable of directly driving external MOSFETs. An internal Zener diode, shown in Figure 12, clamps the driver voltage under 13V to protect the MOSFET gate from over voltage. With integrating circuits to control the slew rate of the switch turn-on rise time, the external resistor RG may not be necessary to reduce switching noise. Gate FAN6754A RG On/Off Logic VDD RS 13V Figure 12. Gate Driver High/Low Line Compensation in HV Pin The conventional pulse-by-pulse current limiting scheme has a constant threshold for the current-limit comparator, which results in a higher power limit for high line voltage. The FAN6754A has a current-limit threshold that decreases as line voltage increases to makes the actual power limit level almost constant over different line voltages within a universal input voltage range, as shown in Figure 13. In the FAN6754A, the peak-current limiting threshold is adjusted by the peak voltage of the HV pin. When the internal circuit detailed in Figure 14 samples the line voltage information, an internal 1.62kΩ resistor is connected to the HV pin to scale down the line voltage by forming a voltage divider with resistor RHV and the internal resistor. Figure 13. Universal Line Voltage Compensation for Constant Output Power Limit Figure 14. HV Sampling Circuit and VLimit Level vs. VIN Brownout Protection in HV Pin As shown in Figure 15, the AC line voltage is monitored by the HV pin using a resistor (RHV), a diode (D1), and an internal line voltage sample circuit. Figure 16 shows brownout protection behavior when the circuit uses the half- wave of the AC line input (VHV) at the HV pin. When the VHV is larger than the brown-in detection voltage threshold (VAC-ON) and VDD is higher than VDD-AC, the PWM begins to operate without any debounce time. Meanwhile, the PWM stops operating when VHV is less than the detection voltage threshold (VAC-OFF) for longer than debounce time. The VAC-ON and VAC-OFF are calculated using the following equations: 2 / ) 6 . 1 6 . 1 9 . 0 ( ) ( ON - AC + × = HV R RMS V (1) . k in is R where or HV OFF - AC Ω + × = 2 / ) 6 . 1 6 . 1 R 81 . 0 ( ) RMS ( V HV (2) 1V 3V VIN (V) 0.39 VLimit (V) 0.46 AC In GND VIN RHV 1.62kΩ Line Sample Circuit |
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