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4

Switching noise spikes will in-

variably be found at the I SENSE

pins. The noise spikes could trip

the current limit threshold which

is only 100 mV. R

should be adjusted so as to reduce

the switching noise well below

100 mV to prevent false current

limiting. The sum of the

DC level plus the noise

peak will determine the

current limiting value.

As in most switching

circuits it may be dif-

ficult to determine the

true noise amplitude without careful attention to grounding

of the oscilloscope probe. Use the shortest possible ground

lead for the probe and connect exactly at the GND terminal of

the amplifier. Suggested starting values are C

R

The required value of R

culated by:

R

where R

maximum desired current. In current mode the required value

of each R

divided down by 2 (see Figure B). If R

divide down the sense voltage. The shutdown divider network

will also have an effect on the filtering circuit.

BYPASSING

Adequate bypassing of the power supplies is required for

proper operation. Failure to do so can cause erratic and low

efficiency operation as well as excessive ringing at the out-

puts. The Vs supply should be bypassed with at least a 1µF

ceramic capacitor in parallel with another low ESR capacitor

of at least 10µF per amp of output current. Capacitor types

rated for switching applications are the only types that should

be considered. The bypass capacitors must be physically

connected directly to the power supply pins. Even one inch of

lead length will cause excessive ringing at the outputs. This is

due to the very fast switching times and the inductance of the

lead connection. The bypassing requirements of the Vcc supply

are less stringent, but still necessary. A .1µF to .47µF ceramic

capacitor connected directly to the Vcc pin will suffice.

MODULATION RANGE

The high side of the all N channel H-bridge is driven by a

bootstrap circuit. For the output circuit to switch high, the low

side circuit must have previously been switched on in order to

charge the bootstrap capacitor. Therefore, if the input signal to

the SA12 demands a 100% duty cycle upon start-up the output

will not follow and will be in a tri-state (open) condition. The

ramp signal must cross the input signal at some point to cor-

rectly determine the output state. After the ramp crosses the

input signal one time the output state will be correct thereafter.

In addition, if during normal operation the input signal drives

the SA12 beyond its linear modulation range (approximately

95%) the output will jump to 100% modulation.

GENERAL

Please read Application Note 30 on "PWM Basics". Refer

to Application Note 1 "General Operating Considerations" for

helpful information regarding power supplies, heat sinking and

mounting. Visit www.apexmicrotech.com for design tools that

help automate pwm filter design; heat sink selection; Apex’s

complete Application Notes library; Technical Seminar Work-

book; and Evaluation Kits.

CLOCK CIRCUIT AND RAMP GENERATOR

The clock frequency is internally set to a frequency of ap-

proximately 400kHz. The CLK OUT pin will normally be tied to

the CLK IN pin. The clock is divided by two and applied to an

RC network which produces a ramp signal at the –PWM/RAMP

pin. An external clock signal can be applied to the CLK IN pin

for synchronization purposes. If a clock frequency lower than

400kHz is chosen an external capacitor must be tied to the

–PWM/RAMP pin. This capacitor, which parallels an internal

capacitor, must be selected so that the ramp oscillates 4 volts

p-p with the lower peak 3 volts above ground.

PWM INPUTS

The full bridge driver may be accessed via the pwm input

comparator. When +PWM > -PWM then A OUT > B OUT. A

motion control processor which generates the pwm signal can

drive these pins with signals referenced to GND.

PROTECTION CIRCUITS

A fixed internal current limit senses the high side current.

Should either of the outputs be shorted to ground the high

side current limit will latch off the output transistors. The tem-

perature of the output transistors is also monitored. Should a

fault condition raise the temperature of the output transistors

to 165°C the thermal protection circuit will latch off the output

transistors. The latched condition can be cleared by either

recycling the V

with a 10V pulse. See Figures A and B. The outputs will remain

off as long as the shutdown pulse is high (10V).

When supply voltage is over 100V, these circuits may not

protect the FET switches in the case of short circuits directly

at the pins of the amplifier. However, a small inductance be-

tween the amplifier and the short circuit will limit current rise

time and the protection circuits will be effective. A pair of 12

inch wires is adequate inductance.

CURRENT LIMIT

There are two load current

sensing pins, I SENSE A and

I SENSE B. The two pins can

be shorted in the voltage

mode connection but both

must be used in the current

modeconnection(seefigures

A and B). It is recommended

that R

ductive. Load current flows in

the I SENSE pins. To avoid errors due to lead lengths connect

the I LIMIT/SHDN pin directly to the R

the filter network and shutdown divider resistor) and connect

the R

OPERATING

CONSIDERATIONS

SA12

This data sheet has been carefully checked and is believed to be reliable, however, no responsibility is assumed for possible inaccuracies or omissions. All specifications are subject to change without notice.

SA12U REV G AUGUST 2007 © 2007 Apex Microtechnology Corp.