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SG3524F Datasheet(PDF) 4 Page - NXP Semiconductors |
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SG3524F Datasheet(HTML) 4 Page - NXP Semiconductors |
4 / 5 page Philips Semiconductors Product specification SG3524 SMPS control circuit 1994 Aug 31 4 TIMING CAPACITOR VALUE (C–)–( µF) 10 5 3 2 1.0 0.5 0.3 .001 .002 .005 .01 .02 .05 1 SL00178 Figure 5. Output Stage Dead Time as a Function of the Timing Capacitor Value 100 50 20 10 5 2 1 100 50 20 10 5 200 5001ms2ms OSCILLATOR PERIOD ( µs) SL00179 Figure 6. Oscillator Period as a Function of RT and CT FREQUENCY - (Hz) 80 60 40 20 0 10 100 1k 10k 100k 1M 10M RL = RESISTANCE FROM PIN 9 TO GND RL = 30kΩ RL = 100kΩ RL = 1MΩ RL = 30MΩ RL = 300kΩ SL00180 Figure 7. Amplifiers Open-Loop Gain as a Function of Frequency and Loading on Pin 9 Oscillator The oscillator in the SG3524 uses an external resistor (RT) to establish a constant charging current into an external capacitor (CT). While this uses more current than a series-connected RC, it provides a linear ramp voltage on the capacitor which is also used as a reference for the comparator. The charging current is equal to 3.6 V ÷ RT and should be kept within the approximate range of 30µA to 2mA; i.e., 1.8k<RT<100k. The range of values for CT also has limits as the discharge time of CT determines the pulse-width of the oscillator output pulse. This pulse is used (among other things) as a blanking pulse to both outputs to insure that there is no possibility of having both outputs on simultaneously during transitions. This output dead time relationship is shown in Figure 5. A pulse width below approximately 0.5 µs may allow false triggering of one output by removing the blanking pulse prior to the flip-flop’s reaching a stable state. If small values of CT must be used, the pulse-width may still be expanded by adding a shunt capacitance ( ≅100pF) to ground at the oscillator output. [(Note: Although the oscillator output is a convenient oscilloscope sync input, the cable and input capacitance may increase the blanking pulse-width slightly.)] Obviously, the upper limit to the pulse width is determined by the maximum duty cycle acceptable. Practical values of CT fall between 0.001 and 0.1 µF. The oscillator period is approximately t=RTCT where t is in microseconds when RT=Ω and CT=µF. The use of Figure 6 will allow selection of RT and CT for a wide range of operating frequencies. Note that for series regulator applications, the two outputs can be connected in parallel for an effective 0-90% duty cycle and the frequency of the oscillator is the frequency of the output. For push-pull applications, the outputs are separated and the flip-flop divides the frequency such that each output’s duty cycle is 0-45% and the overall frequency is one-half that of the oscillator. External Synchronization If it is desired to synchronize the SG3524 to an external clock, a pulse of ≅+3V may be applied to the oscillator output terminal with RTCT set slightly greater than the clock period. The same considerations of pulse-width apply. The impedance to ground at this point is approximately 2k Ω. If two or more SG3524s must be synchronized together, one must be designated as master with its RTCT set for the correct period. The slaves should each have an RTCT set for approximately 10% longer period than the master with the added requirement that CT(slave)=one-half CT (master). Then connecting Pin 3 on all units together will insure that the master output pulse—which occurs first and has a wider pulse width—will reset the slave units. Error Amplifier This circuit is a simple differential input transconductance amplifier. The output is the compensation terminal, Pin 9, which is a high-impedance node (RL≅ 5MΩ). The gain is A V + gMRL + 8 I C RL 2kT [ 0.002R L and can easily be reduced from a nominal of 10,000 by an external shunt resistance from Pin 9 to ground, as shown in Figure 7. In addition to DC gain control, the compensation terminal is also the place for AC phase compensation. The frequency response curves of Figure 7 show the uncompensated amplifier with a single pole at approximately 200Hz and a unity gain crossover at 5MHz. Typically, most output filter designs will introduce one or more additional poles at a significantly lower frequency. Therefore, the best stabilizing network is a series RC combination between Pin 9 and ground which introduces a zero to cancel one of the output filter poles. A good starting point is 50k Ω plus 0.001µF. |
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