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ISL6520ACRZ Datasheet(PDF) 9 Page - Intersil Corporation |
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ISL6520ACRZ Datasheet(HTML) 9 Page - Intersil Corporation |
9 / 12 page 9 FN9016.5 March 28, 2007 equations give the approximate response time interval for application and removal of a transient load: where: ITRAN is the transient load current step, tRISE is the response time to the application of load, and tFALL is the response time to the removal of load. The worst case response time can be either at the application or removal of load. Be sure to check both of these equations at the minimum and maximum output levels for the worst case response time. Input Capacitor Selection Use a mix of input bypass capacitors to control the voltage overshoot across the MOSFETs. Use small ceramic capacitors for high frequency decoupling and bulk capacitors to supply the current needed each time Q1 turns on. Place the small ceramic capacitors physically close to the MOSFETs and between the drain of Q1 and the source of Q2. The important parameters for the bulk input capacitor are the voltage rating and the RMS current rating. For reliable operation, select the bulk capacitor with voltage and current ratings above the maximum input voltage and largest RMS current required by the circuit. The capacitor voltage rating should be at least 1.25 times greater than the maximum input voltage and a voltage rating of 1.5 times is a conservative guideline. The RMS current rating requirement for the input capacitor of a buck regulator is approximately 1/2 the DC load current. For a through hole design, several electrolytic capacitors may be needed. For surface mount designs, solid tantalum capacitors can be used, but caution must be exercised with regard to the capacitor surge currentrating. These capacitors must be capable of handling the surge-current at power-up. Some capacitor series available from reputable manufacturers are surge current tested. MOSFET Selection/Considerations The ISL6520A requires 2 N-Channel power MOSFETs. These should be selected based upon rDS(ON), gate supply requirements, and thermal management requirements. In high-current applications, the MOSFET power dissipation, package selection and heatsink are the dominant design factors. The power dissipation includes two loss components; conduction loss and switching loss. The conduction losses are the largest component of power dissipation for both the upper and the lower MOSFETs. These losses are distributed between the two MOSFETs according to duty factor. The switching losses seen when sourcing current will be different from the switching losses seen when sinking current. When sourcing current, the upper MOSFET realizes most of the switching losses. The lower switch realizes most of the switching losses when the converter is sinking current (see the equations below). These equations assume linear voltage- current transitions and do not adequately model power loss due the reverse-recovery of the upper and lower MOSFET’s body diode. The gate-charge losses are dissipated by the ISL6520A and don't heat the MOSFETs. However, large gate- charge increases the switching interval, tSW which increases the MOSFET switching losses. Ensure that both MOSFETs are within their maximum junction temperature at high ambient temperature by calculating the temperature rise according to package thermal-resistance specifications. A separate heatsink may be necessary depending upon MOSFET power, package type, ambient temperature and air flow. Given the reduced available gate bias voltage (5V), logic-level or sub-logic-level transistors should be used for both N-MOSFETs. Caution should be exercised with devices exhibiting very low VGS(ON) characteristics. The shoot- through protection present aboard the ISL6520A may be circumvented by these MOSFETs if they have large parasitic impedences and/or capacitances that would inhibit the gate of the MOSFET from being discharged below it’s threshold level before the complementary MOSFET is turned on. Figure 7 shows the upper gate drive (BOOT pin) supplied by a bootstrap circuit from VCC. The boot capacitor, CBOOT, develops a floating supply voltage referenced to the PHASE pin. The supply is refreshed to a voltage of VCC less the boot diode drop (VD) each time the lower MOSFET, Q2, turns on. tRISE = L x ITRAN VIN - VOUT tFALL = L x ITRAN VOUT (EQ. 7) PLOWER = Io 2 x r DS(ON) x (1 - D) Where: D is the duty cycle = VOUT / VIN, tSW is the combined switch ON and OFF time, and FS is the switching frequency. Losses while Sourcing Current Losses while Sinking Current P LOWER Io 2 r DS ON () × 1D – () × 1 2 --- Io ⋅ V IN × t SW F S × × + = P UPPER Io 2 r DS ON () × D × 1 2 --- Io ⋅ V IN × t SW F S × × + = PUPPER = Io 2 x r DS(ON) x D (EQ. 8) +5V ISL6520A GND LGATE UGATE PHASE BOOT VCC +5V NOTE: NOTE: VG-S ≈ VCC CBOOT DBOOT Q1 Q2 + - FIGURE 7. UPPER GATE DRIVE BOOTSTRAP VG-S ≈ VCC -VD + VD - ISL6520A |
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