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AD8310 Datasheet(PDF) 16 Page - Analog Devices

Part # AD8310
Description  Fast, Voltage-Out DC-440 MHz, 95 dB Logarithmic Amplifier
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Manufacturer  AD [Analog Devices]
Direct Link  http://www.analog.com
Logo AD - Analog Devices

AD8310 Datasheet(HTML) 16 Page - Analog Devices

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AD8310
Rev. D | Page 16 of 24
NARROW-BAND MATCHING
Transformer coupling is useful in broadband applications.
However, a magnetically coupled transformer might not be
convenient in some situations. Table 5 lists narrow-band
matching values.
Table 5. Narrow-Band Matching Values
FC
(MHz)
ZIN
(Ω)
C1
(pF)
C2
(pF)
LM
(nH)
Voltage Gain
(dB)
10
45
160
150
3300
13.3
20
44
82
75
1600
13.4
50
46
30
27
680
13.4
100
50
15
13
270
13.4
150
57
10
8.2
220
13.2
200
57
7.5
6.8
150
12.8
250
50
6.2
5.6
100
12.3
500
54
3.9
3.3
39
10.9
10
103
100
91
5600
10.4
20
102
51
43
2700
10.4
50
99
22
18
1000
10.6
100
98
11
9.1
430
10.5
150
101
7.5
6.2
260
10.3
200
95
5.6
4.7
180
10.3
250
92
4.3
3.9
130
9.9
500
114
2.2
2.0
47
6.8
At high frequencies, it is often preferable to use a narrow-band
matching network, as shown in Figure 31. This has several
advantages. The same voltage gain is achieved, providing
increased sensitivity, but a measure of selectivity is also
introduced. The component count is low: two capacitors and an
inexpensive chip inductor. Additionally, by making these
capacitors unequal, the amplitudes at INP and INM can be
equalized when driving from a single-sided source, that is, the
network also serves as a balun. Figure 32 shows the response for
a center frequency of 100 MHz; note the very high attenuation
at low frequencies. The high frequency attenuation is due to the
input capacitance of the log amp.
C1
C2
INHI
INLO
AD8310
SIGNAL
INPUT
LM
1
8
Figure 31. Reactive Matching Network
FREQUENCY (MHz)
14
4
–1
60
150
80
100
110
130
3
2
1
0
70
90
120
140
INPUT
GAIN
9
8
7
6
5
13
12
11
10
Figure 32. Response of 100 MHz Matching Network
GENERAL MATCHING PROCEDURE
For other center frequencies and source impedances, the
following steps can be used to calculate the basic matching
parameters.
Step 1: Tune Out CIN
At a center frequency, fC, the shunt impedance of the input
capacitance, CIN, can be made to disappear by resonating with a
temporary inductor, LIN, whose value is given by
IN
IN
C
L
2
1
ω
=
where CIN = 1.4 pF. For example, at fC = 100 MHz, LIN = 1.8 µH.
Step 2: Calculate CO and LO
Now, having a purely resistive input impedance, calculate the
nominal coupling elements, CO and LO, using
()
C
M
IN
O
M
IN
C
O
f
R
R
L
R
R
f
C
π
=
π
=
2
;
2
1
For the AD8310, RIN is 1 kΩ. Therefore, if a match to 50 Ω is
needed, at fC = 100 MHz, CO must be 7.12 pF and LO must be
356 nH.
Step 3: Split CO into Two Parts
To provide the desired fully balanced form of the network
shown in Figure 31, two capacitors C1 and C2, each of
nominally twice CO, can be used. This requires a value of
14.24 pF in this example. Under these conditions, the voltage
amplitudes at INHI and INLO are similar. A somewhat better
balance in the two drives can be achieved when C1 is made
slightly larger than C2, which also allows a wider range of
choices in selecting from standard values.
For example, capacitors of C1 = 15 pF and C2 = 13 pF can be
used, making CO = 6.96 pF.


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